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JP2011508537A - Common wave communication system and method and sideband mitigation communication system and method for increasing communication speed and spectral efficiency and enabling other benefits - Google Patents
Common wave communication system and method and sideband mitigation communication system and method for increasing communication speed and spectral efficiency and enabling other benefits Download PDF
JP2011508537A
JP2011508537A JP2010539903A JP2010539903A JP2011508537A JP 2011508537 A JP2011508537 A JP 2011508537A JP 2010539903 A JP2010539903 A JP 2010539903A JP 2010539903 A JP2010539903 A JP 2010539903A JP 2011508537 A JP2011508537 A JP 2011508537A
ヘイスティングス、ウイリアム
ホーン、ジェイムス
ファルコン ナノ インク.
2008-12-19 Application filed by ファルコン ナノ インク. filed Critical ファルコン ナノ インク.
2011-03-10 Publication of JP2011508537A publication Critical patent/JP2011508537A/en
H04L27/00—Modulated-carrier systems
H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying includes continuous phase systems
H04L27/22—Demodulator circuits; Receiver circuits
H04L25/00—Baseband systems
H04L25/02—Details ; Arrangements for supplying electrical power along data transmission lines
H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks ; Receiver end arrangements for processing baseband signals
H04L25/03006—Arrangements for removing intersymbol interference
H04L25/03178—Arrangements involving sequence estimation techniques
H04L25/03248—Arrangements for operating in conjunction with other apparatus
H04L25/03273—Arrangements for operating in conjunction with other apparatus with carrier recovery circuitry
H04B1/62—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission for providing a predistortion of the signal in the transmitter and corresponding correction in the receiver, e.g. for improving the signal/noise ratio
H04B13/00—Transmission systems characterised by the medium used for transmission, not provided for in groups H04B3/00 - H04B11/00
H04B13/02—Transmission systems in which the medium consists of the earth or a large mass of water thereon, e.g. earth telegraphy
H04B3/00—Line transmission systems
H04B3/02—Details
H04B3/04—Control of transmission; Equalising
H04B3/10—Control of transmission; Equalising by pilot signal
H04L25/0264—Arrangements for coupling to transmission lines
H04L25/0298—Arrangement for terminating transmission lines
H04L25/03828—Arrangements for spectral shaping; Arrangements for providing signals with specified spectral properties
H04L25/03866—Arrangements for spectral shaping; Arrangements for providing signals with specified spectral properties using scrambling
H04L25/08—Modifications for reducing interference; Modifications for reducing effects due to line faults ; Receiver end arrangements for detecting or overcoming line faults
H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
H04L7/00—Arrangements for synchronising receiver with transmitter
H04L7/02—Speed or phase control by the received code signals, the signals containing no special synchronisation information
H04L7/033—Speed or phase control by the received code signals, the signals containing no special synchronisation information using the transitions of the received signal to control the phase of the synchronising-signal-generating means, e.g. using a phase-locked loop
H04L7/0331—Speed or phase control by the received code signals, the signals containing no special synchronisation information using the transitions of the received signal to control the phase of the synchronising-signal-generating means, e.g. using a phase-locked loop with a digital phase-locked loop [PLL] processing binay samples, e.g. add/subtract logic for correction of receiver clock
H04L2025/0335—Arrangements for removing intersymbol interference characterised by the type of transmission
H04L2025/03356—Baseband transmission
H04L2025/03375—Passband transmission
H04L2025/03382—Single of vestigal sideband
Common wave communication systems and methods and sideband mitigation communication systems and methods that can be used with both wireless and wired communication links are provided.
The provided systems and methods can allow for faster data rates, greater immunity to noise, increased bandwidth / spectrum efficiency, and / or other benefits.
Applications include, but are not limited to, cellular phones, smart phones (eg, iPhone, BlackBerry, etc.), wireless Internet, local area networks (eg, WiFi type uses), wide area networks (eg, WiMAX type uses), portable information terminals, There are computers, Internet service providers and communication satellites.
[Selection] Figure 3
PRIORITY CLAIM / RELATED APPLICATIONS This application is filed Dec. 19, 2007, entitled "Common Wave Communication System and Method for Incoming Communication Speeds and US Patent Application No. 61 / or Enabling Other Benefits". , 043 of US Patent Act 119 (e) and priority under US Patent Act 120. This application is incorporated herein by reference in its entirety.
Wired or wireless communication systems and methods are provided.
Various wired and wireless communication systems are well known. For example, as shown in FIGS. 1 and 2, two different conventional communication systems are known. As shown in FIG. 1, an example of a conventional wired communication system includes a transmitter and a receiver, and a data signal is transmitted through a first wired communication link, and the data signal is inverted (in the form of the inverted data signal). Two data signals are transmitted over the second wired communication link. In the system shown in FIG. 1, two wired communication links are located close to each other. The receiver can receive these two data signals, determine the difference between these two data signals, and extract data from these data signals. This conventional communication system is known as a differential signal system, where only a difference between two signals is required, so a lower voltage can be used and a higher data transmission rate is possible, All noise affects both communication links, and noise immunity is increased because the noise is filtered out when the difference between the two data signals is determined. The system shown in FIG. 1 can be used, for example, on a printed circuit board, where each wired communication link is a trace on the printed circuit board.
An example of how the system of FIG. 1 functions on a copper wire is when two adjacent wires each have a signal and one signal is an inverted signal of the other signal. For example, if "digital 1" is transmitted at a level of 1 volt, line A is 1 volt, line B is 0 volt (ie, inverted), and if "digital 0" is transmitted, line A Is 0 volts and line B is 1 volt. Since both of these wires extend from the transmitter to the receiver, the wires can pick up noise that raises or lowers the voltage level in the wire, and in addition can cause spikes that look like data There is. If these two wires are physically close to each other, the noise will be exactly the same for both wires. At the receiver end, these two lines are connected to a differential amplifier circuit. The differential amplifier circuit "removes" this noise by subtraction.
FIG. 2 shows an example of another conventional communication system that can be a wireless communication system. In this communication system, a transmitter generates a plurality of data signals and transmits them over a communication link, and then a receiver independently extracts data from each data signal, but between these data signals, a data signal There is no useful relationship to extract data from. The system shown in FIG. 2 can be used for a general mobile telephone system such as a time division multiplexing communication system and a code division multiplexing communication system.
FIG. 3 shows a wireless communication system that uses a pilot signal, where the pilot signal is modulated with a carrier and data signal to produce a single output signal, which is then transmitted through a communication link to a receiver. Sent to. The receiver then uses the pilot signal (embedded in the output signal) to decode the data signal. In this conventional system using pilot signals, only a single signal is transmitted over the communication link.
None of these conventional communication systems use a data signal and a reference signal (transmitted on different channels over the same communication link) and it is therefore desirable to provide a common wave system and method. Intended for common wave systems and methods.
Furthermore, systems and methods for minimizing effective bandwidth and neutralizing sidebands (sideband mitigation) are provided that can significantly increase data transmission rate and spectral efficiency. Desirably, therefore, such systems and methods are also directed.
It is a figure which shows the conventional communication system. It is a figure which shows the conventional communication system. It is a figure which shows the conventional pilot signal communication system. 1 illustrates one embodiment of a common wave communication system having a transmitter and a receiver. FIG. It is a figure which shows an example of the common wave communication system shown in FIG. 4 in detail. It is a figure which shows an example of the embodiment of the common wave communication system shown in FIG. It is a figure which shows an example of the expected signal for the demodulator circuit in the receiver of a common wave communication system to compare with an input signal. It is a figure which shows an example of a common wave communication method. It is a figure which shows an example of the method of resetting the data signal of a common wave communication system. It is a figure which shows an example of the method of minimizing the effective bandwidth of a communication system. It is a figure which shows an example of the method of minimizing the effective bandwidth of a communication system. It is a figure which shows an example of the filter used with the signal which has an alternating phase. It is a figure which shows an example of the method of neutralizing the sideband of a communication system. It is a figure which shows an example of the method of neutralizing the sideband of a communication system. It is a figure which shows an example of the circuit which produces | generates a 1 GHz carrier wave with an amplitude of 1.414V and a phase of 0 degree. It is a figure which shows an example of the time domain with respect to the 1 GHz carrier wave which is not modulated. It is a figure which shows an example of FFT for 1000 ns of the 1 GHz signal which is not modulated. It is a figure which shows an example of FFT with respect to 1000 ns sample of the 1 GHz signal which is not modulated with a 250 kHz-20 dB mask. FIG. 6 is a diagram illustrating an example of a circuit having a data signal generated by V2 and modulation performed by Phase_Modulator_90_deg. It is a figure which shows an example of the data signal during the first 124 ns. The data bit period is 8 ns. It is a figure which shows an example of a modulation signal. The phase of data bit 1 is 90 °, and the phase of data bit 0 is 0 °. 34 ns is shown. It is a figure which shows an example of FFT of the modulation signal of 125 Mbps and 90 degrees of phase shifts. It is a figure which shows an example of the embodiment of the 1st step in a sideband mitigation circuit. FIG. 6 shows an example of a modulated signal having data bit 1 starting from phase 0 and data bit 0 starting from phase 180. It is a figure which shows an example of FFT from which the 1 GHz lobe was removed. The sidebands are getting worse. FIG. 6 shows 867 MHz and 884 MHz lobes with phase. It is a figure which shows an example of the implementation of the sideband mitigation signal added in order to reduce a 867 MHz lobe. FIG. 6 shows an example of a 867 MHz lobe that has been minimized but still remains. FIG. 6 shows an example of a reduced 868 MHz residual lobe embodiment. It is a figure which shows an example of the embodiment of the signal by which all the sidebands lower than 1 GHz were reduced. It is a figure which shows an example of the embodiment of FFT by which the sideband lower than 1 GHz was reduced by the sideband reduction signal shown in Table 1. It is a figure which shows an example of a phase filtering circuit.
This system and method is particularly applicable to wireless communication systems having a single communication link using discrete hardware circuit-based transmitters and receivers described below, which systems and methods are described in this context. . However, the system and method can be used with wired communication systems (eg, fiber optics, electrical wires, printed circuit board (PCB) traces, etc.) or wireless communication systems (eg, cellular telephone systems, mobile device radio systems, etc.) Can be implemented as a transmitter only or a receiver only and / or software (software transmitter and / or receiver), hardware (shown later or in other embodiments), or a combination of software and hardware ( It will be appreciated that the system and method have greater utility since it can be implemented, for example, as a digital signal processor having firmware or other implementations.
"Mobile devices" according to the present invention include, but are not limited to, cellular phones, personal communication services (PCS), smart phones (eg, iPhone, BlackBerry, etc.), wireless internet cards or circuits for computers, wireless local area networks and Any mobile wireless communication device can be included, including wide area network (eg, WiFi, WiMax, etc.) cards or circuits, satellite phones, GPS tracking devices, and the like. A device that uses the common wave system and method is a mobile device regardless of the type of data that the device is transmitting or receiving. For example, the transmitted or received data can include any type of information including but not limited to voice, data files, video, broadcast, music, telemetry, radio, and the like.
FIG. 4 shows one embodiment of a common wave communication system 400 having a transmitter 401 and a receiver 402. The communication system 400 can further include a communication link 403, which can be a medium capable of transmitting signals between a transmitter and a receiver. This medium can include air, space, water, electrical wires, concentric cables, fiber optics, printed circuit board traces, integrated circuit traces, drilling mud, AC power distribution wiring, and the like. In this communication system, a plurality of channels 406 can be placed in the communication link 403. The communication system includes at least one data channel 404 containing a data signal, at least one reference channel 405 containing a reference signal, and another one or more channels 407 that can contain the data signal or reference signal. Can be included. The communication link for the at least one data channel and the communication link for the at least one reference channel may be the same communication link or different communication links.
In this common wave system, the data signal is known as a data wave having an information signal modulated on a carrier using various modulation techniques such as frequency modulation, amplitude modulation, phase modulation or combinations thereof. is there. The reference signal may be known as a common wave, which is a known frequency signal that serves as a reference wave for the data wave (fixed or can be adjusted in a known manner). In one embodiment, the data wave and the common wave can have different frequencies, but the different frequencies are close to each other. In one embodiment, such as a code division multiple access (CDMA) mobile telephone system using frequency hopping, the data wave and the common wave have different frequencies at any one instant, but because of frequency hopping, the data wave is It can have the same frequency as the common wave at some other instant. In other embodiments, a common wave signal is transmitted at a specific frequency for a predetermined number of cycles, and then the same for a predetermined number of cycles (different from the predetermined number of cycles over which the common wave signal is transmitted). Data wave signals can be transmitted at a frequency or at a different frequency. In other embodiments, the data wave signal and the common wave signal can have the same frequency, a series of common wave signals are transmitted, and then a series of data wave signals are transmitted (or a series of data wave signals are transmitted). A series of common wave signals are then transmitted), and the receiver can be calibrated using the common wave signals to provide some noise filtering on the data wave signals.
In one embodiment of a common wave system, one or more data signals 404 and one or more reference signals 405 are simultaneously transmitted through communication link 403 and received by receiver 402.
In other embodiments, the one or more data signals and the one or more reference signals are not simultaneously transmitted over the communication link. Once the one or more data signals and one or more reference signals are received by the receiver 402, each data signal is compared to a corresponding reference signal to extract an information signal from the data signal. Both the data signal and the corresponding reference signal are similarly affected by the noise in the communication link 403, so that a portion of the noise is filtered out by comparing the data signal with the reference signal at the receiver. This common wave reduces the level of noise in the data signal, resulting in a better signal-to-noise ratio and thus a higher possible transmission rate, as is well known by Shannon's law. The system provides improved noise immunity.
FIG. 5 is a diagram illustrating in more detail an example of the common wave communication system 400 illustrated in FIG. 4, which includes a single data signal channel and a single channel being communicated over a wireless communication link for illustrative purposes. One reference signal channel is shown. As described above, the data signal 404 and the reference signal 405 are communicated over the communication link 403 between the transmitter 401 and the receiver 402. The transmitter 401 can include a modulator 503 that modulates the information signal 502 onto a carrier wave 501 (having a particular frequency) to generate a data signal. In one embodiment, a phase modulator circuit can be used. A common wave signal 405 is generated, but the common wave signal 405 (in the example shown in FIG. 5) is not modulated before transmission. The data signal and the common wave signal are then transmitted to the receiver 402 via the communication link 403 via one or more antennas 505.
The receiver 402 can receive these signals from the communication link using one or more antennas 506, and these signals received by the antennas 506 are tuned to the carrier frequency of the data signal. The first filter 507 and the second filter 508 tuned to the frequency of the reference signal are input. Thus, the first filter allows a data signal to be output to the first input of the signal comparison device 509 (filtering out other signals), and the second filter converts the reference signal into the signal comparison device. Allows output to the second input of 509 (filters out other signals). In one embodiment, the signal comparison device may be a differential amplifier that compares the signal at the first input with the signal at the second input. Accordingly, the signal comparison device 509 outputs a signal that is the difference between the data signal and the reference signal, and this difference removes noise introduced into the communication link 403. In order to generate an information signal 511 corresponding to the information signal 502 input to the transmitter 401, the output of the signal comparison device is supplied to a demodulator 510 (such as the phase demodulator of the example of FIG. 5). Further receives a replica of the carrier (generated locally from the receiver or extracted from the transmitted signal). In one embodiment using a differential amplifier, the output of the differential amplifier can then be analyzed to identify (demodulated) data. This signal is quite different from the normal radio signal being demodulated, but this signal can be analyzed by well known techniques using standard circuitry or a digital signal processor (DSP).
FIG. 6 shows an example of an embodiment of the common wave communication system shown in FIG. In this embodiment, the transmitter 401 further generates a carrier wave such as a 910.546 MHz carrier wave, such as a carrier wave generator 601 such as a voltage controller oscillator, and a reference wave such as a 925.000 MHz reference wave. And a reference wave generator 602 such as a voltage controller oscillator. In this embodiment, modulator 503 may be a phase shifter circuit that shifts the phase of the carrier wave based on information signal 502. In this embodiment, these data signals and reference waves are input to a signal amplifier 603, such as a radio frequency amplifier, that boosts the strength of both of these signals, which are then one or Radiated by a plurality of antennas 505.
The receiver 402 of this embodiment can further include an amplifier 604, such as a low noise amplifier, which boosts the signal strength of the received signal (both data and reference signals), which are then This is supplied to the filters 507 and 508. In this embodiment, the demodulator 510 compares the incoming information signal (output from the signal comparator 509) with the expected signal of "1" or "0" and outputs the recovered information signal. A circuit (such as a threshold circuit). FIG. 7 illustrates the expected signals of "1" and "0" in one embodiment, where "1" starts +90 degrees out of phase with the data wave and "0" is −90 degrees with the data wave. It starts out of phase.
FIG. 8 shows an example of a common wave communication method 800 that can be performed by the transmitter and receiver shown in FIGS. At the transmitter, the system selects a relationship between the data signal and the reference signal (801). This relationship can be communicated to the receiver in several ways (eg, this relationship may be preconfigured or set during each communication session). This relationship can be a specific difference in amplitude, frequency, phase and / or polarity at a specific time. In one embodiment, the system can have default settings (both transmitter and receiver) set, and then the relationship can be adjusted as necessary by communicating with each other. One example of a default relationship is general amplitude, frequency and / or phase modulation, which can be changed during communication to provide frequency hopping and / or adjust signal strength. After determining this relationship, the transmitter can generate (802) a reference signal and a data signal based on the information signal (803). After generating these signals at the transmitter, the data signal is communicated through the data signal channel (804) and the reference signal is communicated through the reference signal channel (805) via one or more communication links 403. The receiver then receives the transmitter signal (806) and then uses the relevant information to extract the information signal from the data signal in the data channel (807), thereby outputting the information signal (808).
FIG. 9 shows an example of a method for resetting the data signal of the common wave communication system. When the reference and data signals are transmitted simultaneously, these two signals are superimposed, which can cause significant destructive interference for most of the time (about 50% of the time). Is common in many wireless systems. In order to overcome this superposition problem, in one embodiment of a common wave communication system using phase modulation, the transmitter periodically resets the data signal so that the data signal is converted to a data signal as shown in FIG. And return to the same phase. In one embodiment, the data wave can be reset every four signal periods (as shown in FIG. 9). This resetting of the data signal can be used not only for phase modulation embodiments, but also for amplitude modulation embodiments, frequency modulation embodiments and other modulation embodiments. This resetting of the data signal can be used not only for a common wave communication system in which the data signal and the reference signal are transmitted simultaneously, but also for a system that does not transmit the data signal and the reference signal simultaneously.
Control of Effective Radiated Power As mentioned above, this common wave system can transmit common waves at a fixed frequency, the common wave signal is substantially unmodulated, the data channels with data signals have different frequencies, The amplitude of the data channel signal has a known relationship to the common wave signal. In one embodiment, the amplitude of the common wave signal can be significantly higher than the data signal, such as 0-20 dB. Then, at the receiver, a very narrow bandpass filter (BPF) detects the common wave signal.
This common wave signal having a fairly high amplitude establishes a strong reference signal for evaluating the frequency, phase, amplitude and / or time of the data signal at the receiver. Hardware, software, digital signal processor (DSP), etc. can use this strong reference signal to distinguish the data signal from noise and to decode / recover the data signal.
As an example, a common wave signal can be transmitted with 100 watts of effective radiated power (ERP), and 8 data channels can be transmitted to 8 different receivers with ERP 50 W, respectively. For this common wave signal, the receiver can have a bandpass filter with a bandwidth of 100 kHz so that the receiver receives a strong signal sampled over a period of 10 microseconds. It is well known that a 100 W signal can penetrate walls and weather better than a 50 W signal and can handle noise, multipath and travel speed. Thus, each of the eight receivers receives a strong common wave signal that is used as a reference for evaluating a particular signal of interest of a particular receiver.
In most practical implementations of communication systems, there is a limit to the power that each transmitter is allowed to transmit. For example, generally in the United States, a mobile telephone tower transmitter is only allowed to transmit ERP 500W, so it is not possible to design an embodiment of a communication system with eight 100W data signals. This is because the transmitter will exceed the maximum power allowed. However, embodiments having a strong common wave signal and multiple data wave signals with lower power allow the communication system to meet the maximum transmission power level and make the data signal more powerful with the higher power common wave signal. Enables accurate decoding / recovery. The higher power common wave signal can be broadcast to multiple receivers each of which can use the common wave signal, resulting in the ratio of the number of common wave signals to the number of data wave signals. Can be 1 to 8 (examples above), 1 to 100, 1 to 1000, or 1 to 1,000,000. In fact, there is no limit to the number of data channels that can use a single common wave signal. The advantage of using more data channels with the same common wave signal is that the proportion of the common wave signal occupies less of the total ERP allowed. In one embodiment, multiple mobile phone service providers using the same cell tower can use the same common wave signal, thereby allowing all service providers to increase ERP for their respective data channels. .
Minimizing Effective Bandwidth FIGS. 10 and 11 illustrate an example method for minimizing the effective bandwidth of a communication system. The methods shown in FIGS. 10-11 can be used in conventional communication systems and common wave communication systems.
In one exemplary communication system, if the carrier frequency is 1 GHz and the digital data is modulated at 10 MHz by AM, FM or PM, the transmitted frequency band is from 990 MHz to 1.010 GHz, which is When it needs to be used as a transmission channel, it causes interference problems with 995 MHz. The resulting increase in bandwidth is one of many factors that limit the total amount of data that can be transmitted in a given frequency band. In order to overcome this interference at 995 MHz and minimize the bandwidth of the carrier, the communication system can use a carrier that is phase shifted 180 degrees at a predetermined time as shown in FIG. For the sake of clarity, the information signal modulated on the carrier is not shown. As shown in FIG. 11, this phase shift zeros the average power at the carrier frequency and nearby channels, eg 995 MHz. Thus, 995 MHz can be used as a communication channel using a common wave system or conventional technology, and this channel is not affected by the 1 GHz channel.
In one embodiment, if the transmitted signal is phase shifted every 10 cycles, the receiver must also "phase" to be able to handle the incoming signal. When adjacent channels also use this phase shift method, the phase shift timing of each channel can be shifted from the other channels. This allows more channels to be packed into the same frequency band without inter-channel interference.
In traditional filters for transmitters or receivers, alternating the phase of the signal as shown in FIG. 10 may prevent the circuit from effectively resonating, and therefore the circuit outputs a weak signal. .
FIG. 12 illustrates one embodiment of an alternating phase signal filter 1200 that effectively achieves resonance for signals having alternating phases. The switch 1201 changes its position alternately based on the switch control input. The timing of this position switch is such that a conventional bandpass filter or resonant circuit 1202 always has the same phase input to it. This allows the circuit to achieve resonance and thus pass a strong signal at the desired frequency and phase. In addition, this causes destructive interference to undesirable frequencies and phases. This same type of alternating phase signal filter 1200 works well when used with a reset signal as shown in FIG.
In the embodiment shown in FIG. 10, the carrier is phase shifted 180 degrees, but other combinations of phase shifts can achieve similar results, and the system is capable of achieving the 180 degree phase shift shown in FIG. It can be understood that the present invention is not limited to. For example, a 0 degree 10 carrier, a 120 degree 10 carrier, and a -120 degree 10 carrier have lower average power at the carrier frequency than a 0 degree 30 wave. Further, different phase, amplitude and frequency combinations can have similar effects and are within the scope of this disclosure.
Sideband Neutralization FIGS. 13 and 14 show an example of a method for neutralizing a sideband of a communication system. The methods shown in FIGS. 13-14 can be used with conventional communication systems and common wave communication systems. Changing the radio signal (amplitude, frequency and / or phase) increases the bandwidth and creates sidebands. Sidebands are an integral part of many protocol wireless communications, such as "single sideband" wireless communications. However, in many situations, sidebands are an undesirable byproduct of signal modulation.
As shown in FIG. 11, it can be seen that considerable sidebands are generated by the phase shift of the carrier signal. These sidebands are undesirable because they are radiated and interfere with another channel at that frequency. The traditional method of eliminating sidebands is the use of low-pass, high-pass or bandpass filters. These traditional filters degrade high speed signals and are not desirable in situations where high speed data signals are involved. In a sideband neutralization method that can be used with a common wave system, a "neutralization signal" can be injected into the transmission line along with the carrier signal. As shown in FIG. 13, to neutralize the 950 MHz sideband, a 950 MHz signal having a specific predetermined amplitude and phase is used to neutralize the sideband, and FIG. The signal obtained as a result of neutralizing the sidebands is shown. For example, the injected signal has the same amplitude as the neutralizing sideband and needs to be 180 degrees phase shifted from the neutralizing sideband. In the example shown in FIG. 13, the carrier wave has an amplitude of 1 volt (see FIG. 10) and the injected 950 MHz signal has an amplitude of 0.6525 volts. The injected signal starts 90 degrees out of phase with the carrier. In addition, additional signals can be injected in a similar manner to eliminate other sidebands.
As long as the amplitude, frequency and phase of the sidebands are known in advance, signal injection into the transmission line can be used to eliminate sidebands generated from all sideband sources. These values can be determined from previous transmissions in the laboratory environment and used in field settings. Even when a sideband is generated by data modulation, an appropriate sideband neutralization signal can be injected into the transmission line. The details of the neutralization signal vary depending on the data value.
At the receiver end of the transmission system, the original carrier is recovered using known techniques. If neutralization signals are injected, the injected neutralization signals are removed to recover the original carrier.
A "transmission line" according to the present invention is defined as any path used to transfer signal energy from one location to another. Transmission lines include, but are not limited to, conductors within the transmitter, waveguides, lines connecting the transmitter to a communication link including one or more antennas, amplifiers or wireless communication links, and the like.
Next, a detailed example of the above-described sideband neutralization (sideband reduction) will be described. In this description, simulation is used to illustrate the neutralization of the sidebands. The following example shows how neutralization of sidebands can substantially increase the spectral efficiency of wireless communications. In this example, a well-known signal is shown as a starting point, and then for comparison purposes, a signal that utilizes the described sideband mitigation. For purposes of this example, a 1 GHz carrier is used, but the disclosed sideband mitigation can be used with any frequency and is therefore not limited to a particular frequency. This exemplary frequency is used for common frequencies such as mobile phones (800, 900, 1800, 2100 MHz), WiFi (2.4 GHz), WiMax (2.3, 2.5 and 3.5 GHz). This is because it is close to the belt. For the purpose of this example, the simulation software used is LTspice / SwitcherCAD III Version 2.24i from Linear Technology Corporation.
A circuit capable of generating a 1 GHz carrier wave for this example is shown in FIG. The voltage source generates a sine wave having an amplitude of 1.414 V and a frequency of 1 GHz. Simulating this circuit in the time domain gives a voltage versus time oscilloscope output as shown in FIG. FIG. 17 shows the result of executing a well-known FFT (Fast Fourier Transform) simulation for this signal voltage. For the purposes of this example, all FFT operations are performed for a period of 1000 ns using a Hamming window function, 1,048,576 data point samples, and 5-point binomial smoothing, unless otherwise specified. Executed.
To show how the Federal Communications Commission (FCC) regulations apply, "CFR Title 47, Part 15—Radio Frequency Equipment, Sections 15.247 902-928 MHz, 2400-2483.5 MHz, and 5725— Referring to "Operation in 5850 MHz" (CFR Title 47, Part 15-Radio Frequency Devices, §15.24.7 Operation within the bands 902-928 MHz, 2400-2483.5 MHz, and 5725-5850 MHz) Has been.
§15.247 Operation in the 902-928 MHz, 2400-2483.5 MHz and 5725-5850 MHz bands (a) Operation under the provisions of this section is limited to frequency hopping and digital modulation intentional radiators in accordance with the following provisions:
(1) The frequency hopping system shall have hopping channel carrier frequencies separated by the greater of 25 kHz minimum or 20 dB bandwidth of the hopping channel, whichever is greater; . . .
The power for the carriers shown above is 20 mW, lower than the maximum level for those bands and 1 GHz. FIG. 18 shows the result of drawing a 250 kHz (20 dB) bandwidth mask while paying attention to the FFT result. In this figure, since the FFT is only sampled for 1000 ns, the signal does not fit within the mask.
In order to add data to this carrier wave, a data signal is generated by V2 in FIG. 19 and output to TP_Data.
The following data for this example is arbitrarily selected.
10110011 100001111 00001111 10000011 111110000 00111111 10000000 11111111
00000000 11111111 10000000 00111111 11110000 00000111 11111111 10000000
The data rate is 125 Mbps and the period is 8 ns. The first 124 ns of this signal is shown in FIG.
Phase_Modulator_90_degree shown in FIG. 19 modulates a carrier wave with a data wave, and data bit "1" is phase shifted by 90 ° and data bit "0" is phase shifted by 0 °. FIG. 21 shows the first 36 ns of the modulated signal. FIG. 22 shows the FFT of a modulated signal having significant sidebands. As expected, the data rate is so high that the lobe does not fit within the mask. As shown in FIG. 22, the 20 dB bandwidth is 22 MHz.
The sideband mitigation system disclosed herein increases the spectral efficiency defined as follows.
(Spectral efficiency) = (data rate) / (bandwidth) (Equation 1)
Using Equation 1, the spectral efficiency of the signal shown in FIG.
SE −20 dB = (125 Mbps) / (22 MHz) = 5.7 Mbps / MHz
Attempts to improve the spectral efficiency of the signal of FIG. 21 using a bandpass filter (general solution) are not effective because the bandpass filter filters out the data. However, spectral efficiency can be improved using known techniques including reducing delta phase shift to less than 90 ° (eg, 11.5 °), amplitude modulation and other uses. These known techniques work and are used frequently, but have limitations due to the real world noise and sensitivity of the hardware. For example, reducing the delta phase shift to 11.5 ° makes the receiver more susceptible to phase noise (jitter) and approaches the limit of resolution of the phase detector. Therefore, this general solution has limitations and / or does not provide satisfactory results. The sideband mitigation techniques disclosed herein provide an improvement over these known techniques and, in fact, can be used with these known techniques to reduce sidebands and improve spectral efficiency. Can be increased.
To achieve the disclosed sideband mitigation, the central lobe shown in FIG. 22 can be examined. As shown in FIG. 23, a 250 MHz clock with output TP_CLK_250 and a phase shift modulator with output TP_FN1 can be added. Because of this phase shift modulator, the phase shift of each data bit is 0 for half of the data period and 180 for the remaining half. If the data bit is 1, the phase of the data bit is 0 for the first half and 180 for the next half. When the data bit is 0, the phase of the data bit is 180 for the first half and the phase is 0 for the next half, as shown in FIG. In LTspice (simulation software used in this example), "^" (shown in FIG. 23) converts those expressions to both sides of the Boolean, and then converts the resulting XOR (exclusive OR) Is an operand.
Due to the modulation of the sideband mitigation technique, each data bit cancels itself with respect to the FFT, so that the 1 GHz lobe is rejected as shown in FIG. 25, while the remaining lobes in FIG. Worse than before. Focusing on 867 MHz in FIG. 25 and adding the phase, FIG. 26 is obtained. In this figure, the center of the lobe is at 867 MHz, the peak is −11.7 dB, and the phase is −24 ° (1 GHz is −7 °). In order to reduce the 867 MHz lobe, a sine wave V (TP_FN2) having 867 MHz, an amplitude of 0.368 V, and a phase of 245 ° is added to the signal. The result is TP_FN2 and is shown in FIGS.
FIG. 28 shows that residual lobes remain from the first mitigation attempt. In order to reduce the 868 MHz lobe, an 868.6 MHz lobe with an amplitude of 0.200 and a phase of 250 ° is added. These results are shown in FIG. These steps can be repeated to eliminate all lobes above the -20 dB mask, thereby allowing the 125 Mbps data rate to fit within the 250 kHz bandwidth FCC allocation. Using this number in Equation 1, the spectral efficiency of the sideband mitigation system is:
SE -20 dB = (125 Mbps) / (250 kHz) = 500 Mbps / MHz
This value is much higher than the spectral efficiency of existing technology. According to this standard formula, it can be said that the actual spectral efficiency is infinite. The SBM signal shown in Table 1 below eliminates all lobes below 1 GHz, and the resulting signal is shown in FIG. 30 and the FFT in FIG.
The appropriate characteristics of the neutralization signal can be determined by the formula in which the data to be transmitted is input or by a matching table in which the data to be transmitted is used.
Phase filtering When information signals in data waves are phase modulated, phase filtering is useful for demodulation at the receiver. Phase modulation is particularly beneficial for incoming signals that have noise and interference from nearby data channels. In one example, assume that an incoming signal has the desired data in the signal, but the data portion of the signal is obscured by noise and interference in the signal. In order to perform phase filtering, the value of the data is assumed (eg 1 or 0) and a signal equal to the assumption is injected into the incoming signal. If the data value assumption is correct, constructive interference between the incoming signal and the injected signal provides constructive interference and proves that the assumption is correct. If the data value assumption is incorrect, destructive interference indicates that the assumption is incorrect. If the incoming signal and the injected signal are in a resonant (or "tuned") circuit, the difference in output signal between the correct and incorrect assumptions will be very large. This is because the correct assumptions on the injected data and the incoming data portion of the data signal increase the amplitude of the output signal from wave to wave.
In one embodiment shown in FIG. 32, the incoming signal can be split 1505 and input to two circuits, one circuit 1501 assuming that the data is "1" and the other circuit 1502. Assume that the data is "0". Signal generators 1503 and 1504 generate signals equal to their respective assumptions of 1 and 0, respectively. Resistor 1506 is used to add the input signal to the simulated signal. If all four resistors shown have the same value, all signals are added equally. Different values of resistors can be used if gain is required for a particular signal. The outputs from these two circuits can be passed to the signal comparator 1507, which outputs a signal that strongly indicates which assumption ("0" or "1") is the correct assumption. I will provide a. This output signal is quite different from the normal radio signal to be demodulated, but can be analyzed by well known techniques using standard circuits or digital signal processors (DSPs).
In this disclosure, hardware circuits have been shown throughout to show how specific signals can be generated, but these signals and hardware functions are not limited to digital signal synthesis, waveforms Note that they can be integrated by various means including generators, arbitrary waveform generators, signal generators, function generators, digital pattern generators, frequency generators, frequency synthesis, direct digital synthesis and the like. For purposes of this disclosure, these terms and various hardware solutions are all synonymous and are all within the scope of this disclosure.
In the foregoing, reference has been made to a particular embodiment of the invention, but those skilled in the art will appreciate that changes can be made to this embodiment without departing from the principles and spirit of the invention. The scope of the present invention is defined by the appended claims.
A transmitter for simultaneously transmitting a plurality of channels across a communication link, the plurality of channels further comprising at least one data signal channel carrying data information and a reference signal having a predetermined relationship with the data signal; At least one reference channel for carrying the data information based on the at least one reference channel when the data information in the data signal channel is transmitted across the communication link having unknown characteristics. A communication device that can recover.
A receiver separated from the transmitter by the communication link, further comprising a receiver for receiving the plurality of simultaneous channels, the receiver comprising the at least one data based on the at least one reference channel; The apparatus of claim 1, comprising a data extractor that extracts the data information from a channel.
The apparatus of claim 2, wherein the data extractor determines a difference between the at least one data channel and the at least one reference channel to extract the data information from the at least one data channel.
The apparatus of claim 1, wherein the at least one reference channel does not carry data information.
The apparatus of claim 1, wherein the at least one reference channel does not carry data information during the period in which the at least one data channel carries data information.
The apparatus of claim 1, wherein the at least one reference channel and the at least one data channel are transmitted over a single transmission medium.
The apparatus of claim 6, wherein the communication link further comprises a wired communication link.
The apparatus of claim 7, wherein the wired communication link further comprises one of a wire, a concentric cable, an optical fiber, a printed circuit board trace, an integrated circuit trace, a drilling mud, and an AC power distribution line.
The apparatus of claim 6, wherein the communication link further includes a wireless communication link that functions through a medium transmitting the plurality of channels, the medium further including one of air, space, or water.
The apparatus of claim 1, wherein the reference signal has more power than the at least one data signal.
The apparatus of claim 1, wherein the reference signal is used by a plurality of mobile device service providers.
A receiver for simultaneously receiving a plurality of channels across a communication link, the plurality of channels further comprising at least one data signal channel carrying data information and a reference signal having a predetermined relationship with the data signal; Carrying the data information based on the at least one reference channel when the data information in the data signal channel is received across the communication link having unknown characteristics. A communication device that can recover.
The apparatus of claim 12, further comprising a data extractor that extracts the data information from the at least one data channel based on the at least one reference channel.
The apparatus of claim 13, wherein the data extractor determines a difference between the at least one data channel and the at least one reference channel to extract the data information from the at least one data channel.
The apparatus of claim 12, wherein the at least one reference channel does not carry data information.
The apparatus of claim 12, wherein the at least one reference channel does not carry data information during the period in which the at least one data channel carries data information.
The apparatus of claim 12, wherein the at least one reference channel and the at least one data channel are transmitted over a single transmission medium.
The apparatus of claim 17, wherein the communication link further comprises a wired communication link.
The apparatus of claim 18, wherein the wired communication link further comprises one of electrical wires, concentric cables, fiber optic elements, printed circuit board traces, integrated circuit traces, drilling mud water and AC power distribution lines.
The apparatus of claim 17, wherein the communication link further includes a wireless communication link that functions through a medium transmitting the plurality of channels, the medium further including one of air, space, or water. .
The apparatus of claim 12, wherein the reference signal has more power than the at least one data signal.
The apparatus of claim 12, wherein the reference signal is used by a plurality of mobile device service providers.
A communication apparatus comprising a receiver capable of receiving the signal by adjusting how the alternating phase signal is input to the tuning circuit.
A circuit that transmits an input signal to a plurality of circuits, each of the plurality of circuits comparing a resulting combined signal with a circuit that combines an expected possible signal with the input signal. And a comparator for determining which signal is closest to one of another set of expected signals.
Equipped with a transmitter that can transmit the channel across the transmission line,
The transmitter further comprises a carrier source that provides a carrier wave having a certain frequency, and a circuit that changes the characteristic of the carrier wave, thereby changing the characteristic of the carrier wave, thereby changing the average power of the carrier wave at the frequency. Greatly reduces communication equipment.
The characteristic of the carrier further includes a phase of the carrier, and the circuit for changing the characteristic of the carrier further provides the phase of the carrier in a manner that significantly reduces average power at the carrier frequency. 26. The apparatus of claim 25, comprising a circuit for shifting.
The circuit that changes the characteristics of the carrier further includes a neutralized signal having a characteristic that neutralizes one or more sidebands at one or more sideband frequencies of the carrier. A neutralization signal generator that injects into the transmission line, the neutralization signal interfering destructively with the one or more sidebands at one or more sideband frequencies; 26. The device of claim 25.
28. The apparatus of claim 27, wherein the characteristic of the neutralization signal is determined by an expression into which data to be transmitted is input.
28. The apparatus of claim 27, wherein the characteristic of the neutralization signal is determined by a matching table in which data to be transmitted is used.
28. The apparatus of claim 27, wherein the characteristic of the carrier is selected from the group consisting of the phase of the carrier, the amplitude of the carrier, and the frequency of the carrier.
26. The apparatus of claim 25, wherein the circuit that changes the characteristic of the carrier further comprises a modulator.
Equipped with a receiver that can receive the channel across the transmission line,
A communication apparatus, further comprising: a circuit that receives the sideband neutralized carrier having the changed characteristics and recovers the carrier from the sideband neutralized carrier.
33. The apparatus of claim 32, wherein the altered characteristic of the carrier further includes a phase of the carrier, and the circuit that recovers the carrier shifts the phase of the carrier to generate the carrier. .
33. The apparatus of claim 32, wherein the circuit for recovering the carrier further comprises a circuit for removing the neutralized signal having certain characteristics from the sideband neutralized carrier to recover the carrier. .
The apparatus of claim 32, wherein the circuit for recovering the carrier further comprises a modulator.
Providing data information and transmitting multiple channels simultaneously across a communication link,
The plurality of channels further includes at least one data signal channel carrying data information and at least one reference channel carrying a reference signal having a predetermined relationship with the data signal, wherein the data signal channel in the data signal channel A communication method capable of recovering the data information based on the at least one reference channel when the data information is transmitted across the communication link having unknown characteristics.
38. The method of claim 37, further comprising receiving the plurality of simultaneous channels and extracting the data information from the at least one data channel based on the at least one reference channel.
Extracting the data information further comprises determining a difference between the at least one data channel and the at least one reference channel to extract the data information from the at least one data channel. 39. The method according to item 38.
40. The method of claim 38, wherein the at least one reference channel does not carry data information.
40. The method of claim 38, wherein the at least one reference channel does not carry data information during the period in which the at least one data channel carries data information.
40. The method of claim 38, wherein the at least one reference channel and the at least one data channel are transmitted over a single transmission medium.
Providing a carrier wave having a certain frequency, and changing the characteristic of the carrier wave, wherein the average power of the carrier wave at the frequency is significantly reduced by changing the characteristic of the carrier wave.
44. The method of claim 43, wherein changing the characteristic of the carrier further comprises shifting the phase of the carrier in a manner such that average power at the carrier frequency is significantly reduced.
Changing the characteristic of the carrier further comprises a neutralized signal having a characteristic that neutralizes one or more sidebands at one or more sideband frequencies of the carrier. 44. The method of claim 43, comprising injecting into the transmission line, wherein the neutralized signal interferes destructively with the one or more sidebands at one or more sideband frequencies. the method of.
44. The method of claim 43, wherein the characteristic of the carrier is selected from the group consisting of the phase of the carrier, the amplitude of the carrier, and the frequency of the carrier.
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text:
He's been a bad, bad rake—and it takes a governess to teach him a lesson
The accidental governess
After her livelihood slips through her fingers, Alexandra Mountbatten takes on an impossible post: transforming a pair of wild orphans into proper young ladies. However, the girls don't need discipline. They need a loving home. Try telling that to their guardian, Chase Reynaud: duke's heir in the streets and devil in the sheets. The ladies of London have tried—and failed—to make him settle down. Somehow, Alexandra must reach his heart... without risking her own.
The infamous rake
Like any self-respecting libertine, Chase lives by one rule: no attachments. When a stubborn little governess tries to reform him, he decides to give her an education—in pleasure. That should prove he can't be tamed. But Alexandra is more than he bargained for: clever, perceptive, passionate. She refuses to see him as a lost cause. Soon the walls around Chase's heart are crumbling... and he's in danger of falling, hard.
Avon Romance
Erica – ☆☆☆☆
4 Unexpectedly Humorous Stars
The Governess Game is the second installment of the Girl Meets Duke series. I've yet to read the first in the series, so I can attest that this novel could easily be read as a standalone. However, it did whet my appetite to go back and purchase the first novel.
Alexandra is an original heroine, meaning she wasn't cookie-cutter in nature. As an orphan, who originally was raised on a ship by her captain father, she now calibrates clocks. An accidental meeting with the hero of the novel leads to misunderstandings and an unexpected offer of employment.
Chase. Chase is by far one of my favorite historical romance heroes, but not in a broody, heart-aflutter sense. As the guardian of two little girls, the unexpected heir to a duke is beside himself. Rosamond and Daisy... those girls are something else. They were an utter delight of pure chaos. Reading Chase give eulogy after eulogy for Daisy's doll... they were by far the sweetest, most hilarious passages I've ever read.
Not wishing to give a byplay of the plot and scenes... Chase and Alex fit. Their interactions were filled with banter and tension, which lent a realistic edge to the romance that is oftentimes slightly forced in this genre. Organic, Chase and Alex built a friendship of sorts while learning how to handle the girls together. Butting heads was just a form of verbal foreplay for the couple, fueling my need to turn the pages.
But for me, what won me over was Rosamond and Daisy. They offered an unbelievable amount of innocent humor that had me chuckling repeatedly as I read. As a close second, the banter is an honorable mention. Not feeling forced or over-the-top, every interaction between Chase and Alex was entertaining, either putting a smile or a blush on my face.
Definitely recommend to historical romance fans and fans of the author. I'll be checking out Tessa Dare's backlist as I anxiously await the next in the series.
TESSA DARE is the New York Times and USA Today bestselling author of twenty historical romances. Her books have won numerous accolades, including Romance Writers of America's prestigious RITA® award (twice) and the RT Book Reviews Seal of Excellence. Booklist magazine named her one of the "new stars of historical romance," and her books have been contracted for translation in more than a dozen languages.
A librarian by training and a booklover at heart, Tessa makes her home in Southern California, where she lives with her husband, their two children, and a trio of cosmic kitties.
Connect with Tessa
The Secret Society of Damsels Who Dare Facebook Group
Reviewers on the Wicked Reads Review Team were provided a free copy of The Governess Game (Girl Meets Duke #2) by Tessa Dare to read and review.
Labels: 4 star, Erica, Girl Meets Duke Series, Historical Romance, Reviews, Tessa Dare

redpajama_set_name: RedPajamaCommonCrawl


text:
UPDATE ON THE FOOT-AND-MOUTH DISEASE OUTBREAK IN LIMPOPO
The Department encourages livestock owners to limit the movement of cloven hoofed animals until the extent of the outbreak has been fully determined.
Four further cases of Foot and Mouth Disease (FMD) were reported since mid-December 2019, with 3 cases reported in December and 1 case reported in the first week of January 2020. The total number of confirmed positive locations since the start of outbreak has risen to fifteen (15).
More than 130 points were identified with possible links to specific auctions and known affected properties. Follow-up investigations and collection of samples were already performed on 95 of these points and precautionary quarantine has been lifted on 44 properties that have been proven negative for FMD.
All properties where the disease has been confirmed have been placed under quarantine and cloven hoofed animals are not allowed to move off the quarantined properties. Guidelines and application procedures have been finalized for animals on FMD quarantined properties to undergo early slaughter at designated abattoirs with specific conditions to prevent the spread of FMD. FMD does not affect people therefore meat and milk from infected livestock is safe for human consumption
The Department, together with the Provincial Veterinary Services, started conducting awareness on FMD clinical signs and biosecurity measures in Limpopo Province during the week of 4th December. Awareness was already conducted in 6 villages in the Molemole area and 315 farmers attended these sessions.
The use of FMD vaccine has not been indicated in controlling the current outbreak. The vaccination of cattle against FMD is conducted only by state veterinary officials in specific areas determined by the Director Animal Health, free of charge. FMD vaccine is a controlled product that may only be handled by Veterinary Service, the general public is urged to immediately notify state veterinary officials should there be a suspicion of someone having, or claiming to have or sell FMD vaccine.
The prohibition on the gathering of cloven hoofed animals from two or more properties, for distribution to two or more properties, has been published in the Government Gazette on 4 December 2019 and is applicable to the whole country.
This resulted after the Veterinary Authorities identified that the short-term congregation and redistribution of cloven hoofed animals played an integral part in the spread of the disease in this outbreak as all the affected properties have been linked directly or indirectly to auctions. This notice does not prohibit the movement of livestock from farm to farm, or private auctions at individual farms. The gazetted notice is available on the DAFF website
https://www.daff.gov.za/daffweb3/Home/Foot-and-mouth.
In order to bring normality to the trade of livestock, the Department and the FMD Technical Task Team urge all auctioneers to register with the Agricultural Produce Agents Council (APAC). This is a legal requirement and auctioneers must comply with the conditions laid down in the Agricultural Produce Agents Act, 1992 (Act 12 of 1992). Additional biosecurity measures to be applied by registered auctioneers are under discussions and will be communicated as soon as finalised.
The Department encourages livestock owners to limit the movement of cloven hoofed animals until the extent of the outbreak has been fully determined. If movements are necessary, the buyers are advised to request health declarations before any animals are bought from sellers, to prevent the possible infection of new properties by positive animals being brought in. Private vets are asked to assist their clients by providing health declarations that indicate that the herd of origin has been inspected and found to be free of clinical signs of FMD and that all animals have been on the farm for at least 28 days before inspection. This will provide additional guarantees that FMD infected animals could not have been introduced onto the farm in that period.
Livestock owners should remain vigilant for clinical signs of FMD in their animals. Any suspected cases of FMD should please be reported to the nearest State Veterinary Office or the nearest veterinarian for further investigation. Owners who have bought from known infected properties are also encouraged to report this to the Provincial Veterinary Authorities for speedy follow up investigations.
Reggie Ngcobo
Media Liaison Officer
Dr Botlhe Modisane
Technical spokesperson on FMD
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The Convict Ship Neva | An Irish Maritime Tragedy on Australian Shores
TOPICS:AustraliaConvict ShipIrish ShipsNeva
Posted By: Ann Robinson 13th May 2020
On 13th May 1835 the convict ship Neva transporting Irish prisoners was wrecked off the coast of Tasmania. It was one of the largest maritime disasters in Australian history and one of the greatest tragedies in nearly a century of convict transportation. Yet in Ireland it's mostly unknown overshadowed by disasters closer to home like the Lusitania, Leinster and Titanic.
But the Neva, carrying so many Irish people, is an important piece of our maritime history and deserves to be remembered every bit as much.
Convict ship Bound for Australia, the Mount Stuart Elphinstone
In January 1835 the Neva set sail from Cork. The three-masted barque was formerly used to transport goods and was refitted with a second deck to serve as a prison. Its destination was a penal colony in Van Diemen's Land (now Tasmania).
On board were 150 female convicts as well as nine free women, many of whom were wives of men already banished. There were also 55 children, mostly very young babies. The crimes of the women varied from petty theft, prostitution to more heinous crimes but the punishment for all was nothing less than exile.
By the time the ship had reached the Australian coast in May 1835, the total number on board had reached 239, with the deaths of a crewman, one convict, one free woman and a birth.
Facts and figures. Credit King Island Maritime Trail
On 13th May 1835, in the early hours of the morning when prisoners were still locked below deck, the ship struck a reef. The ship had run off course into shallower waters during the night but by the time they crew noticed it was too late. The Neva began to break up and water poured in below decks. The woman and children rushed to the upper deck but there wasn't enough boats to save them.
Passengers and crew swarmed onto the few boats that were there but they floundered under the weight. In the end only 22 made it to land and of them another 7 of them died during the night from exposure and exhaustion. The remaining 15 survivors set up camp salvaging what they could from the remains of the ship and were rescued six weeks later.
The death toll was 224, nine of the crew and only six female passengers survived.
A survivor's account
Rose Ann Hyland was one of the most troublesome convicts aboard the Neva. Here is her account of her amazing escape:
"When the ship struck, I was in bed in the black hole that night … The Captain ordered the ladder to be hauled up, and that we, who had been in the black hole, were to be kept down, but myself and other two succeeded in getting on deck. Most of the other Women, who had been in the main prison, had got on deck and into the Cuddy where they were drinking, and some of them were so drunk as to be unable to help themselves. I was on the Poop when the Ship opened, and … I stuck to this part of the Wreck, and went some part of the way on Shore upon it. When we came close to another part of the Wreck, upon which were some of the Sailors, I endeavoured to get upon it, when one of the Sailors caught hold of me and pulled me upon it. I fell off and was a second time caught hold of by the same man, and placed again upon the Wreck. When we got near the shore, this man (Sharp) jumped off the wreck and carried a Boy on Shore; he returned for me, and then for another woman."


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UK's Biggest Community Energy Company Switches On New Solar Farm
Community energy stepped up and delivered the best month ever for the sector, raising £12.8m last November. During the great energy rush of that month the race was on for energy cooperatives with projects already set up to be eligible for EIS tax relief needing to be pushed through before any unforeseen changes to community renewable energy tax relief in the Finance Bill.
In tandem with this, solar community projects had to move quickly to ensure that they could complete planned projects despite the sudden and dramatic digression of Feed-in-tariff (FiT) rates. Again, community energy is fighting back with the number of bencomms projects surging.
£10m fund-raise in the heart of the community
Bristol Energy Cooperative found itself right in the heart of these changes, starting a challenging £10m fund-raise back in October 2015 before the end of EIS, and racing to raise this total before the FiT pre-registration deadlines. We are now in August finishing off the last few smaller installations and can now safely say that we have made it!
Our community energy success does seem part of a wider momentum around the world to increase participation in the transition to local, clean energy generation. £10 million is a huge step up for us (to put it in context we raised around £250,000 in our first two share offers together).
COP 21's climate agreement (though we would have liked more) was a major step in the right direction. The debate certainly pushed the financial dangers of climate change into the mainstream with warnings from the World Bank, while the opportunities of positive investments in renewables were espoused by top corporate leaders including Bill Gates and Mark Zuckerberg.
Crowdfunding via the positive investment platform Ethex raised £3.5m for our solar projects. We offered two options for investment: a share offer with 5% anticipated returns and bond offers (2 and 3 year) with 6% anticipated returns. Debt finance from banks and several other institutions made up the balance. The low £50 minimum share offer investment aims to widen the opportunities for participation in community-owned energy.
The investment is already working for the benefit of the community and the environment, as well as bringing financial returns to investors. We developed a new 4.2 MWp solar farm at Lawrence Weston in Bristol, bought a commercially developed 4.6 MWp solar farm in Somerset, near Hinkley Point, and are installing solar panels on community roofs across Bristol.
So how did we make this happen?
The power of partnerships
Our new solar farm at Lawrence Weston in Bristol is a powerful demonstration of how a community energy co-op, local people, and both corporate and local authority partners can come together to participate in the renewables revolution.
Since our formation in 2011, we've been developing sustainable partnerships, and this time we extended those relationships. For this particular project at Lawrence Weston, Bristol City Council, Social and Sustainable Fund and Triodos Bank provided debt finance to help ensure that we made the FiT deadline.
We had already worked in partnership with Bristol City Council on a community solar rooftop programme. Community energy is a winner for councils up and down the country, struggling with funding cuts but still facing low carbon targets; it helps to meet these targets, lowers energy costs and involves the community to take ownership of energy generation.
The site in Lawrence Weston which sits in a narrow strip of land between two motorways was transformed into an operational solar farm with just an eight week build time. The associated benefits to the local economy as well as furthering the transition to clean, green energy will last much longer.
Local partner, Ambition Lawrence Weston, a community-led regeneration organisation, will along with other local groups benefit from a Community Energy Fund derived from surplus profits. With current generation capacity Bristol Energy Coop's projects are projected to put more than £4m into this fund over the next 25 years. We anticipate this sum increasing as more generating capacity is installed and that projects funded by it will themselves hasten the transition to greater energy sustainability.
The Bristol effect
But the work is really just beginning. Ultimately, we aim to reduce carbon emissions and help our home city of Bristol reach its zero carbon target well before 2050.
Bristol has a deserved reputation for being independent and doing things differently. In fact, our share offer investors could go the extra mile in keeping it local, by investing in our share offer in the local currency, Bristol Pounds. At a grassroots level, we were one of the 850 organisations in the Bristol European Green Partnership which formed the driving force in helping the city become European Green Capital in 2015. The sheer ambition of our fund-raise certainly built on the buzz of the green capital year with a strong will to leave a lasting legacy for the city.
Indeed Bristol and nearby Bath are now firmly on the map as a key area for ethical investments which offer environmental and social benefits as well as attractive financial returns. In April, we became the UK's largest generator of energy by capacity, and were more than happy to be overtaken by fellow cooperative Bath and West Community Energy (BWCE) as they add more community-owned capacity to the National Grid.
Community energy – supply and demand
So, what's next? In terms of energy generation we aim to continue increasing our capacity, not only in solar, but in other technologies as the business opportunities arise. Taking it a stage further, community energy could be about to transform the nature of energy supply in the UK. Along with partner community organisations we are aiming, following a controlled market entry period starting in the autumn, to be part of a new energy supply business launch in spring 2017. It will sell energy direct from community-owned renewables projects like ours with competitively priced tariffs for customers. This is an exciting development as it will bring more control over the whole energy cycle with potential for more efficient and locally beneficial energy use.
Our membership has more than doubled during our latest fund-raise and we now have over 800 members and investors. And we're in good company with the latest Co-operatives UK Economy Report showing that between 2012 and 2016 the number of UK community energy coops rose from 83 to 224, with membership increasing from 10,828 to 16,880 and turnover almost doubling from £4.9m to £8.9m.
This clearly illustrates strong interest in making the transition to renewables as the way to power cities and communities. At Bristol Energy Cooperative we believe this transition should happen more quickly than the current speed of change that government policy is driving. We also believe that rapid transition to a more sustainable energy economy is perfectly possible and we aim to continue demonstrating this through growing our business.
We have created an infrastructure that allows individuals, business and other organisations to benefit in the short term whilst contributing to this longer term energy transformation; so essential for our future sustainability and resilience. And we encourage more people to come aboard.
A more supportive national policy framework would be helpful and Bristol Energy Cooperative will continue to campaign and lobby for this alongside initiatives such as Climate Coalition's week of action in October. For us, the work goes on to mobilise the power of community.
Related Topics:Bill GatesBristolBristol city councilBristol Energy CooperativeClimate ChangeClimate CoalitioncrowdfundingEnergyenergy policyGlobal WarmingMark ZuckerbergReneable energySolar Energy
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